Apparatuses, sense circuits, and methods for compensating for a wordline voltage increase

ABSTRACT

Apparatuses, sense circuits, and methods for compensating for a voltage increase on a wordline in a memory is described. An example apparatus includes a bitline, a memory cell coupled to the bitline, a bipolar selector device coupled to the memory cell, a wordline coupled to the bipolar selector device, and a wordline driver coupled to the wordline. The apparatus further includes a model wordline circuit configured to model an impedance of the wordline and an impedance of the wordline driver, and a sense circuit coupled to the bitline and to the model wordline circuit. The sense circuit is configured to sense a state of the memory cell based on a cell current and provide a sense signal indicating a state of the memory cell. The sense circuit is further configured to adjust a bitline voltage responsive to an increase in wordline voltage as modeled by the model wordline circuit.

CROSS REFERENCE TO RELATED APPLICATION

This application is a divisional of U.S. patent application Ser. No.14/713,878, filed May 15, 2015, which is a divisional of U.S. patentapplication Ser. No. 13/775,868, filed Feb. 25, 2013, U.S. Pat. No.9,042,190 issued on May 26, 2015, which applications and patent areincorporated herein by reference in their entirety.

TECHNICAL FIELD

Embodiments of the invention relate generally to electronic memories,and more particularly, in one or more of the illustrated embodiments, tocompensating for increasing wordline voltage caused by leakage currentsfrom memory cell selectors.

DESCRIPTION OF RELATED ART

Certain memory architectures are susceptible to current leakage from abitline through a bipolar selector device to a wordline during memoryaccess operations. Current leakage through the bipolar selector deviceto the wordline can lead to an increased wordline voltage, which maycause fluctuations in current of a sense signal provided on the bitline.That is, an increased wordline voltage may reduce the voltage margin toaccurately read the sense signal used to sense the data stored by amemory cell. As a result, the reduced voltage margin may lead toinaccurate reading of a memory cell.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of a particular illustrative embodiment of anapparatus including a model wordline circuit and sense circuit;

FIG. 2 is a block diagram of a particular illustrative embodiment of anapparatus including a model wordline circuit and sense circuit;

FIG. 3 is a block diagram of a particular illustrative embodiment of adual output amplifier circuit;

FIG. 4 is a block diagram of a particular illustrative embodiment of amodel wordline driver; and

FIG. 5 is a block diagram of a memory including a model wordline circuitand sense circuit according to an embodiment of the disclosure.

DETAILED DESCRIPTION

Certain details are set forth below to provide a sufficientunderstanding of embodiments of the disclosure. However, it will beclear to one having skill in the art that embodiments of the disclosuremay be practiced without these particular details. Moreover, theparticular embodiments of the present disclosure described herein areprovided by way of example and should not be used to limit the scope ofthe disclosure to these particular embodiments.

Referring to FIG. 1, a particular illustrative embodiment of anapparatus including a model wordline circuit and sense circuit isdisclosed and generally designated 100. The apparatus may be anintegrated circuit, a memory device, a memory system, an electronicdevice or system, a smart phone, a tablet, a computer, a server, etc.The apparatus 100 may compensate for a voltage increase on the wordlineduring a read operation due to current leakage through a selectordevice, such as a bipolar selector device. The apparatus 100 may includea plurality of bitlines 124(0-N). As illustrated in FIG. 1, each bitline124(0-N) is coupled to a respective memory cell 130(0-N) that is coupledin series with a respective selector device 140(0-N). The selectordevices 140(0-N) are illustrated in FIG. 1 as PNP bipolar junctiontransistors. Other types of circuits may be used for the selectordevices 140(0-N) without departing from the scope of the presentdisclosure. Although FIG. 1 illustrates one memory cell 130(0-N) foreach bitline 124(0-N), a plurality of memory cells may be coupled toeach bitline. Embodiments of the disclosure may be used with bitlinescoupled to one or more memory cells. A base of each selector device140(0-N) may be coupled to a wordline 160. The apparatus 100 may furtherinclude a plurality of sense circuits 120(0-N) that are each configuredto sense a respective cell current ICELL(0-N) flowing through therespective bitline 124(0-N). The respective ICELL(0-N) current indicatesa state of the corresponding memory cell 130(0-N). Each of the sensecircuits 120(0-N) compares the respective ICELL(0-N) current withcurrent generated based on a reference voltage SVREF(0-N). TheSVREF(0-N) voltage may be adjusted based on an impedance of a wordlineand wordline driver. The SVREF(0-N) voltage may be adjusted by a modelwordline circuit 110.

The model wordline circuit 110 may include a first model wordline driver112 and a second model wordline driver 114, each coupled to a modelwordline 118. The first model wordline driver 112 and the second modelwordline driver 114 may each model at least one of a first wordlinedriver and a second wordline driver (e.g., wordline drivers 150 and 152)to drive a voltage on the model wordline 118. The model wordline 118 maybe of a similar material and/or have similar electrical characteristicsof the wordline 160. The model wordline resistance components 116(0-N)may model impedance along at least a portion of the wordline 160.

Each of the sense circuits 120(0-N) may be coupled to a respectivebitline 124(0-N) and may be configured to may drive the respectiveICELL(0-N) current along the respective bitline 124(0-N). Further, eachof the sense circuits 120(0-N) may be coupled to the model wordlinecircuit 110 and may be configured to provide a respective model sensecurrent ICELLM(0-N) to the model wordline 118. Each of the sensecircuits 120(0-N) may also provide a respective sense out signal SENSEOUT(0-N) which may indicate the state of the respective memory cell130(0-N).

Each of the memory cells 130(0-N) may be configured to store data. In anembodiment, each of the memory cells 130(0-N) may include a phase changememory material. The phase change memory material may be in one of atleast two states, for example, an unprogrammed state and a programmedstate. The phase change memory material may have a distinct impedancefor each state. In an embodiment, the phase change memory material mayinclude a chalcogenide alloy, such as an alloy of germanium, antimonyand tellurium (GeSbTe), called GST.

In operation, during a memory access operation, each of the sensecircuit 120(0-N) may precharge each respective bitline 124(0-N) to theSVREF voltage prior sensing. In addition, the first wordline driver 150and the second wordline driver 152 drive an memory access voltage alongthe wordline 160 to enable each of the selector device 140(0-N). When aselector device 140(0-N) is enabled, the corresponding ICELL(0-N)current flows through the respective memory cell 130(0-N). The magnitudeof the ICELL(0-N) current is based on the state (e.g., impedance) of therespective memory cell 130(0-N). Based on the respective ICELL(0-N)current, each of the sense circuits 120(0-N) may provide a respectiveSENSE OUT(0-N) signal. A magnitude of the SENSE OUT(0-N) signalindicates the state of the respective memory cell 130(0-N), and,accordingly, may indicate a data value stored by the respective memorycell 130(0-N).

The selector devices 140(0-N) may leak current through the bases to thewordline 160. For example, FIG. 1 depicts cell current ICELL L(0-N) andcell current ICELL R(0-N) leaking through the base of a selector device140(0-N) to the wordline 160. The current leakage causes an increase involtage of the wordline because the wordline 160, the first wordlinedriver 150, and the second wordline driver 152 have non-zero impedances.The wordline voltage increase may reduce base-emitter voltages VEB ofthe selector devices 140(0-N). As a consequence, the ICELL(0-N) currentfor each sense circuit 120(0-N) may be reduced. The magnitude of currentleakage through the base of each selector device 140(0-N) may depend ona gain (B) of the selector device 140(0-N), an impedance of the wordline160, an impedance of the first wordline driver 150 and the secondwordline driver 152, and a state of the corresponding memory cell130(0-N).

In some embodiments, compensation for increased wordline voltageresulting from the leakage current may be dynamically adjusted and maybe based on several dependencies. For example, each of the sensecircuits 120(0-N) may use the model wordline circuit 110 to compensatefor the increased wordline voltage by modeling the increase in wordlinevoltage, and compensating (e.g., increasing) the SVREF voltage by anamount that is based on the voltage increase. Compensating the SVREFvoltage may increase the ICELL currents, and, thus improve the voltagemargin for sensing the ICELL currents.

To model the increase in wordline voltage, each of the sense circuits120(0-N) drives a respective model cell current ICELL M(0-N) through themodel wordline 118 and through at least one of the first wordline driver112 and the second wordline driver 114, similar to the ICELL current ofthe wordline 160. For example, the ICELL M(0-N) current may be dividedinto two components, for example, model cell current ICELL ML(0-N) andmodel cell current ICELL MR(0-N). Responsive to the ICELL M(0-N) currentdriven through the model wordline 118 and through at least one of thefirst model wordline driver 112 and the second model wordline driver 114by a corresponding sense circuit 120(0-N), the corresponding sensecircuit 120(0-N) may use a voltage differential along the model wordline118 (e.g., based on the model wordline resistance 116(0-N) and animpedance of the first model wordline driver 112 and the second modelwordline driver 114) to adjust (e.g., increase) the correspondingSVREF(0-N) voltage. Responsive to adjustment of the correspondingSVREF(0-N) voltage by the corresponding sense circuit 120(0-N), thecorresponding ICELL(0-N) current along the respective bitline 124(0-N)is adjusted (e.g., increased). Increasing, for example, the ICELL(0-N)current (responsive to the adjusted corresponding SVREF(0-N)) tocompensate for the increased wordline voltage may increase the accuracyof the data sensed from a memory cell 130(0-N) during a read operation.

While FIG. 1 depicts the apparatus 100 with at least three bitlines124(0-N), the apparatus 100 may include any number of bitlines.Similarly, although one wordline 160, and associated wordline drivers150, 152, and selector devices 140(0-N) are illustrated in FIG. 1, theapparatus may include any number of wordlines, and associated wordlinedrivers, and selector devices. Also, each of the model wordlineresistance components 116(0-N) may represent impedance of a portion ofthe model wordline 118.

Compensating for increased wordline voltage, which may cause a decreasein the sense signal, by using the model wordline circuit 110 mayincrease the voltage margin for sensing the ICELL currents, and improvesense accuracy of each of the sense circuits 120(0-N). The sensecircuits 120(0-N), in conjunction with the model wordline circuit 110,may provide a dynamic compensation solution by using a model of therespective ICELL(0-N) current through the bitline to determine theincreased current.

Referring to FIG. 2, a particular illustrative embodiment of anapparatus including a model wordline circuit and sense circuit isdisclosed and generally designated 200. The apparatus 200 may representa single sense circuit for a single bitline. The apparatus 200 mayinclude a sense circuit 220 that uses a wordline model circuit 210 toprovide an adjusted sense reference voltage signal SVREFM to compensatefor increased wordline voltage which may be caused by current leakagealong the wordline. The sense circuit 220 is coupled to a memory cell230 though a bitline 226. An impedance of the bitline is represented bybitline load 280. A selector device 240, such as a bipolar selectordevice, is coupled to the memory cell 230 and is configured to selectthe memory cell 230 for memory access responsive to being activated by awordline coupled to a base of the selector device 240. The wordline andassociated wordline driver are represented by wordline and driver(s) 250as impedances RWLDR and RWL. The wordline model circuit 210 includes aRWLDRM component and a RWLM resistive component to model the impedancesRWLDR and RWL, respectively, of the wordline driver(s) and wordline 250.The RWLDRM component may model the RWLDR impedance and a gain (B) of theselector device 240. For example, an impedance of the RWLDRM componentmay be approximately equal to RWLDR/(β+1). The RWLM resistive componentmay model the RWL impedance and the β gain of the bipolar device 240.For example, an impedance of the RWLM resistive component may beapproximately equal to RWL/(β+1). The RWLDR impedance may represent aword line driver impedance, such as an impedance of at least one of thefirst wordline driver 150 and the second wordline driver 152 of FIG. 1.The RWL impedance may present at least a portion of impedance of awordline, such as at least a portion of an impedance of the wordline 160of FIG. 1.

The sense circuit 220 also provides an sense output signal SENSEOUTbased on a comparison between a voltage of an amplifier output signalAMPOUT and a bitline voltage VBL. The sense circuit 220 may include anamplifier 222 to provide the AMPOUT signal, and further include acomparator 228 to perform the comparison. The model wordline circuit 210may include at least a portion of the model wordline circuit 110 ofFIG. 1. The sense circuit 220 may include one of the sense circuits120(0-N) of FIG. 1. The memory cell 230 and the selector device 240 mayinclude at least one of the memory cells 130(0-N) and the selectordevices 140(0-N), respectively, of FIG. 1. The wordline and driver(s)250 may include at least a portion of the first wordline driver 150, thesecond wordline driver 152 and the wordline 160 of FIG. 1.

The amplifier 222 may be a differential amplifier configured to receivethe SVREFM voltage from the model wordline circuit 210 at a first input.The amplifier 222 may be further configured to receive a bitline voltageVBL at a second input. The amplifier 222 may produce the AMPOUT signalat a first output and an model amplifier output signal AMPOUTM at asecond output, each based on the first input and the second input. TheAMPOUTM signal may be fed back to the first input of the amplifier 222.In an embodiment, the AMPOUTM signal is approximately equal to theAMPOUT signal.

The comparator 228 may be configured to receive the AMPOUT signal at afirst input and to receive the VBL voltage at a second input. The firstinput of the comparator 228 may be coupled to the second input of thecomparator 228 via the limiter circuit 224. The AMPOUT signal may be fedback to the bitline via the limiter circuit 224. In an embodiment, thelimiter circuit 224 may include a diode pair coupled in parallel, withthe diode D0 having a forward direction from the first input to thesecond input and a diode D1 having a forward direction from the secondinput to the first input. In an alternative embodiment, the limitercircuit 224 may include a resistive component. The limiter circuit 224may limit a voltage differential between the first input and the secondinput.

In operation, a reference current IREF is provided to the bitline 226.The IREF current is a constant current provided to the bitline during aread operation. Based on the reference current, the bitline 226 isprecharged to approximately the SVREF voltage (e.g., the VBL voltage isapproximately equal to the SVREF voltage) via the AMPOUT signal of theamplifier 222 provided to the bitline 226 through the D0 diode of thelimiter circuit 224. The SVREF voltage may be approximately equal to theSVREFM voltage. When the selector device 240 is enabled, an ICELLcurrent, which may depend on the state of the memory cell and the IREFcurrent, begins to flow through the bitline 226. As the ICELL currentflows, current may leak through the base of the selector device 240through the wordline and driver(s) 250. The current leakage may cause anincrease in wordline voltage (e.g., near the base of the selector device240), and consequently, may result in a reduction in read margin. Theincrease in wordline voltage may be equivalent to a voltage SVA across aword line driver impedance RWLDR, plus a voltage SVB across a word lineimpedance RWL.

The amplifier 222 provides an AMPOUTM signal responsive to the increasein wordline voltage that causes a model cell current ICELLM to flowthrough the wordline model circuit 210. The ICELLM current flowingthrough the wordline model circuit 210 may cause a voltage of the SVREFMsignal to change by the sum voltage of SVAM and SVBM. The change in theSVREFM signal models the increase in wordline voltage due to the currentleakage through the base of the selector device 240 (e.g., SVA+SVB). Theamplifier 222 responds by providing an AMPOUT signal that adjusts theVBL voltage (through the limiter circuit 224) to compensate for theincreased wordline voltage (e.g., VBL=SVREF+SVA+SVB). The comparator 228may compare the voltage of the AMPOUT signal to the VBL voltageresponsive to selection by the selector device 240 and provide theSENSEOUT signal. The SENSE OUT signal may represent a state (e.g.,impedance) of the memory cell 230.

In an embodiment, the first input of the amplifier 222 is anon-inverting input. Thus, feeding back the AMPOUTM signal to the firstinput of the amplifier 222 forms a positive feedback system. To preventinstability (e.g., oscillation) in the positive feedback system, theRWLDRM impedance and/or the RWLM impedance may be adjusted to result ina feedback gain of the positive feedback system of less than one. Anexample of adjusting the model wordline driver impedance is discussedfurther with reference to FIG. 4.

The sense circuit 220 could be replicated for a plurality of bitlines inan array, such as the apparatus of claim 1. Also as would be obvious toone of ordinary skill in the art, the RWL impedance and the RWLDRimpedance may vary for each bitline based on a location along thewordline and variances in characteristics of each individual bipolardevice 240.

Referring to FIG. 3, a particular illustrative embodiment of a dualoutput amplifier circuit is disclosed and generally designated 300. Thedual output amplifier circuit 300 may include an amplifier 322. Theamplifier 322 may be configured to receive an adjusted sense referencevoltage signal SVREFM from a model wordline circuit 310 at a first inputand a bitline voltage VBL at a second input. The amplifier 322 may alsobe configured to provide an amplifier output signal AMPOUT from a firstoutput and an model amplifier output signal AMPOUTM from a secondoutput. The model wordline circuit 310 may include at least a portion ofthe model wordline circuit 110 of FIG. 1, and/or the model wordlinecircuit 210 of FIG. 2. The amplifier 322 may include the amplifier 222of FIG. 2, and may be included in the sense circuit 120 of FIG. 1 and/orthe sense circuit 220 of FIG. 2.

The amplifier 322 may be a differential amplifier configured to receivethe SVREFM voltage from the model wordline circuit 310 at a gate of asecond transistor 352 and a bitline voltage VBL at a gate of a fourthtransistor 362 and a gate of a sixth transistor 372. The amplifier 322may be provide the AMPOUT signal at a first output node between a thirdtransistor 360 and the fourth transistor 362 and the AMPOUTM signal at asecond output node between a fifth transistor 370 and the sixthtransistor 372. The AMPOUT and the AMPOUTM signals may each be based onthe first input and the second input. The AMPOUTM signal may be fed backto the gate of the second transistor 352. In an embodiment, the AMPOUTMsignal is approximately equal to the AMPOUT signal.

The second transistor 352 and a first transistor 350 may form a firstcurrent mirror circuit with the fourth transistor 362 and the thirdtransistor 360. For example, the first transistor 350 coupled in serieswith the second transistor 352. A source of the first transistor 350 isconfigured to receive a first power source (e.g., a VCC power source)and a source of the second transistor 352 is configured to receive asecond power source (e.g., a ground power source). A gate of the firsttransistor 350 is coupled to the drain of the second transistor 352. Agate of the second transistor 352 is configured to receive the SVREFMvoltage that is adjusted by the model wordline circuit 310. A source ofthe third transistor 360 is configured to receive the first power sourceand a source of the fourth transistor 362 is configured to receive thesecond power source. A gate of the third transistor 360 is coupled tothe gate of the first transistor 350 and a gate of the fourth transistor362 is configured to receive the VBL voltage. The AMPOUTM signal may beprovided at a node between the third transistor 360 and the fourthtransistor 362. The AMPOUTM signal is fed back to the gate of the secondtransistor 352.

Additionally, the second transistor 352 and a first transistor 350 mayform a second current mirror circuit with the sixth transistor 372 andthe fifth transistor 370. For example, the fifth transistor 370 iscoupled in series with the sixth transistor 372. A source of the fifthtransistor 370 is configured to receive the first power source and asource of the sixth transistor 372 is configured to receive the secondpower source. A gate of the fifth transistor 370 is coupled to the gateof the first transistor 350 and a gate of the sixth transistor 372configured to receive the VBL voltage. The AMPOUT signal is provided ata node between the fifth transistor 370 and the sixth transistor 372. Inan embodiment, the first current mirror circuit is nearly identical tothe second current mirror circuit.

As would be obvious to one ordinarily skilled in the art, the amplifier322 could be implemented using other amplifier architectures, such as anamplifier using bipolar junction transistors. The amplifier 322 mayprovide the AMPOUT signal and the AMPOUTM signal having characteristicsthat attempt to equalize the VBL voltage received at the gate of thesixth transistor 372 and/or the fourth transistor 362 with the SVREFMvoltage received at the gate of the second transistor 352.

Referring to FIG. 4, a particular illustrative embodiment of an modelwordline driver is disclosed and generally designated model wordlinedriver 400. The model wordline driver 400 may be configured to model awordline driver impedance. The model wordline driver 400 may beconfigured to receive a sense reference voltage signal SVREF and providean output voltage VOUT. The model wordline driver 400 may include thefirst model wordline driver 112 and/or the second model wordline driver114 of FIG. 1. The model wordline driver 400 may be included in theRWLDRM component of the model wordline circuit 210 of FIG. 2, and/or themodel wordline circuit 310 of FIG. 3.

The model wordline driver 400 may be a follower circuit that includes afirst transistor 430 and a second transistor 432 coupled in series, andfurther includes and a third transistor 440 and a fourth transistor 442coupled in series. A drain of the first transistor 430 is coupled to afirst power source (e.g., a VCC power source) via a first currentregulator 420 and a drain of the second transistor 432 is coupled to asecond power source (e.g., a ground power source) via a second currentregulator 422. A gate of the first transistor 430 may be coupled to thedrain of the first transistor 430. A gate of the second transistor 432may be coupled to the drain of the second transistor 432.

A drain of the third transistor 440 is coupled to the first power sourceand a drain of the fourth transistor 442 is coupled to the second powersource. A gate of the third transistor 440 may be coupled to the gate ofthe first transistor 430. A gate of the fourth transistor 442 may becoupled to the gate of the second transistor 432. An output resistanceROUT 450 may be coupled to a node between the third transistor 440 andthe fourth transistor 442, and the VOUT voltage may be provided via theROUT 450. The ROUT 450 may be configured to model an impedance at anoutput of a wordline driver, such as the wordline drivers 150 and 152 ofFIG. 1.

In operation, the SVREF voltage is received at a node between the firsttransistor 430 and the second transistor 432. A current I1 along a paththrough the first transistor 430 and the second transistor 432 iscontrolled by a first current regulator 420 and a second currentregulator 422. A current I2 flows along a path through the thirdtransistor 440. A model cell current ICELLM flows through the ROUTresistance 450 and into a node between the third transistor 440 and thefourth transistor 442. Thus, a current including the current I2 plus theICELLM current flows through the fourth transistor 442. The current I1is adjusted to control the current flowing through the fourth transistor442. A voltage differential between the SVREF voltage and the VOUTvoltage may be indicative of an apparent resistance through the fourthtransistor 442 that models a impedance associated with a word linedriver.

The second current regulator 422 may be implemented using other voltagecontrol circuits or adjustable resistance circuits to model theresistance of the word line driver.

FIG. 5 illustrates a memory 500 according to an embodiment of thepresent invention. The memory 500 includes a memory array 530 with aplurality of memory cells. The memory cells may be non-volatile memorycells, such as NAND flash cells, phase change memory cells, or maygenerally be any type of memory cells.

Command signals, address signals and write data signals may be providedto the memory 500 as sets of sequential input/output (“I/O”) signalstransmitted through an I/O bus 528. Similarly, read data signals may beprovided from the memory 500 through the I/O bus 528. The I/O bus 528 isconnected to an I/O control unit 520 that routes the signals between theI/O bus 528 and an internal data bus 522, an internal address bus 524,and an internal command bus 526. The memory 500 also includes a controllogic unit 510 that receives a number of control signals eitherexternally or through the command bus 526 to control the operation ofthe memory 500.

The address bus 524 applies block-row address signals to a row decoder540 and column address signals to a column decoder 550. The row decoder540 and column decoder 550 may be used to select blocks of memory ormemory cells for memory operations, for example, read, program, anderase operations. The column decoder 550 may enable write data signalsto be applied to columns of memory corresponding to the column addresssignals and allow read data signals to be coupled from columnscorresponding to the column address signals.

In response to the memory commands decoded by the control logic unit510, the memory cells in the array 530 are read, programmed, or erased.Read, program, and erase circuits 568 coupled to the memory array 530receive control signals from the control logic unit 510 and includecurrent generators for generating various reference currents for read,program and erase operations. The read, program and erase circuits 568may be coupled to a model wordline circuit 525. The model wordlinecircuit 525 may include the model wordline circuit 110 of FIG. 1, themodel wordline circuit 210 of FIG. 2, the model wordline circuit 310 ofFIG. 3, the model wordline driver 400 of FIG. 4 and/or any combinationthereof. For example, the model wordline circuit 525 may be configuredto compensate for current leakage along a wordline by modelingcorresponding impedance of a wordline and a wordline driver to increasea corresponding cell current flowing through a memory cell used a readoperation. The read, program and erase circuits 568 may include thesense circuit 120(0-N) of FIG. 1, the sense circuit 220 of FIG. 2, theamplifier 322 of FIG. 3, and/or any combination thereof. In addition tothe signal line drivers in the row decoder 540 and/or column decoder550, one or more of the voltage generators or other read, program, anderase circuits 568 may also include signal line drivers.

After the row address signals have been applied to the address bus 524,the I/O control unit 520 routes write data signals to a cache register570. The write data signals are stored in the cache register 570 insuccessive sets each having a size corresponding to the width of the I/Obus 528. The cache register 570 sequentially stores the sets of writedata signals for an entire row or page of memory cells in the array 530.All of the stored write data signals are then used to program a row orpage of memory cells in the array 530 selected by the block-row addresscoupled through the address bus 524. In a similar manner, during a readoperation, data signals from a row or block of memory cells selected bythe block-row address coupled through the address bus 524 are stored ina data register 580. Sets of data signals corresponding in size to thewidth of the I/O bus 528 are then sequentially transferred through theI/O control unit 520 from the data register 580 to the I/O bus 528.

Those of ordinary skill would further appreciate that the variousillustrative logical blocks, configurations, modules, circuits, andalgorithm steps described in connection with the embodiments disclosedherein may be implemented as electronic hardware, computer softwareexecuted by a processor, or combinations of both. Various illustrativecomponents, blocks, configurations, modules, circuits, and steps havebeen described above generally in terms of their functionality. Whethersuch functionality is implemented as hardware or processor executableinstructions depends on the particular application and designconstraints imposed on the overall system. Skilled artisans mayimplement the described functionality in varying ways for eachparticular application, but such implementation decisions should not beinterpreted as causing a departure from the scope of the presentdisclosure.

The previous description of the disclosed embodiments is provided toenable a person skilled in the art to make or use the disclosedembodiments. Various modifications to these embodiments will be readilyapparent to those skilled in the art, and the principles defined hereinmay be applied to other embodiments without departing from the scope ofthe disclosure. Thus, the present disclosure is not intended to belimited to the embodiments shown herein but is to be accorded the widestscope possible consistent with the principles and novel features asdefined by the following claims.

What is claimed is:
 1. A sense circuit comprising: an amplifierconfigured to provide a first signal and a second signal, wherein thefirst signal and the second signal are based on a bitline voltage and asense reference voltage adjusted based on an impedance of at least aportion of a wordline, wherein the bitline voltage is received at afirst input and the sense reference voltage adjusted based on animpedance of at least a portion of a wordline is received at a secondinput, wherein the first signal is fed back to the second input; and acomparator configured to provide an output signal indicating a state ofa memory cell based on a voltage of the second signal and the bitlinevoltage.
 2. The sense circuit of claim 1, wherein the amplifiercomprises: a first transistor coupled in series with a secondtransistor, wherein a source of the first transistor is configured toreceive a first power source and a drain of the second transistor isconfigured to receive a second power source, wherein a gate of the firsttransistor is coupled to a drain of the first transistor and wherein agate of the second transistor is configured to receive the sensereference voltage that is adjusted by a word line model circuit; a thirdtransistor coupled in series with a fourth transistor, wherein a sourceof the third transistor is configured to receive the first power sourceand a source of the fourth transistor is configured to receive thesecond power source, wherein a gate of the third transistor is coupledto the gate of the first transistor and a gate of the fourth transistoris configured to receive the bitline voltage, wherein the first signalis provided at a node between the third transistor and the fourthtransistor; and a fifth transistor coupled in series with a sixthtransistor, wherein a source of the fifth transistor is configured toreceive the first power source and a source of the sixth transistor isconfigured to receive the second power source, wherein a gate of thefifth transistor is coupled to the gate of the first transistor and agate of the sixth transistor is configured to receive the bitlinevoltage, wherein the second signal is provided at a node between thefifth transistor and the sixth transistor.
 3. The sense circuit of claim2, wherein the first signal is fed back to the gate of the secondtransistor.
 4. The sense circuit of claim 1, further comprising alimiter circuit coupled to the first and second inputs of thecomparator.
 5. The sense circuit of claim 4, wherein the limiter circuitcomprises a first diode coupled in parallel with a second diode betweenthe first input and the second input, wherein the first diode includes aforward direction from the first input to the second input and thesecond diode includes a forward direction from the second input to thefirst input.
 6. The sense circuit of claim 4, wherein the limitercircuit comprises a resistive component.
 7. The sense circuit of claim1, wherein the second input is a non-inverting input and the firstsignal forms a positive feedback loop.
 8. A sense circuit comprising: anamplifier configured to receive an adjustable reference voltage at afirst input and a bitline voltage at a second input, the amplifierfurther configured to provide a first signal and a second signal,wherein the first signal and the second signal are based, at least inpart, on the adjustable reference voltage and the bitline voltage; and acomparator configured to receive the second signal at a first input nodeand the bitline voltage at a second input node, and provide an outputsignal based, at least in part, on a comparison of the second signal andthe bitline voltage.
 9. The sense circuit of claim 8, wherein theadjustable reference voltage is based, at least in part, on a voltage ofa model wordline circuit.
 10. The sense circuit of claim 9, wherein theadjustable reference voltage is based, at least in part, on the firstsignal.
 11. The sense circuit of claim 10, wherein the amplifier isconfigured to increase a voltage of the first signal responsive to anincrease in the voltage of the model wordline circuit.
 12. The sensecircuit of claim 8, further comprising a limiter circuit coupled betweenthe first input node of the comparator and the second input node of thecomparator.
 13. The sense circuit of claim 12, wherein the limitercircuit comprises: a first diode forward coupled between the firstsignal and the second signal; and a second diode forward coupled betweenthe second signal and the first signal, wherein the second diode iscoupled in parallel with the first diode.
 14. The sense circuit of claim8, wherein the output signal of the comparator is indicative of a valuestored on a memory cell coupled to a bitline having the bitline voltage.15. An apparatus comprising: a wordline circuit having a wordlinevoltage; a model wordline circuit configured to provide a referencevoltage; a bitline coupled to the wordline and configured to carry abitline voltage; and a sense circuit configured to receive the referencevoltage and the bitline voltage and to provide a first signal and asecond signal, wherein the first signal is indicative of an increase inthe wordline voltage and the second signal is indicative of a value of amemory cell coupled to the bitline.
 16. The apparatus of claim 15,wherein sense circuit comprises: an amplifier configured to receive thereference voltage and the bitline voltage and provide the first signaland an amplifier output signal; and a comparator configured to receivethe amplifier output signal and the bitline voltage and to provide thesecond signal.
 17. The apparatus of claim 16, further comprising: alimiter circuit configured to adjust the bitline voltage to compensatefor an increase in the wordline voltage.
 18. The apparatus of claim 17,further comprising: a selector circuit configured to couple the bitlineand the wordline, wherein the wordline voltage increases responsive tocurrent leakage from the bitline through the selector device to thewordline.
 19. The apparatus of claim 15, wherein the first signal iscoupled to the reference voltage.
 20. The apparatus of claim 15, whereinthe sense circuit comprises: a first transistor coupled in series with asecond transistor, wherein a gate of the second transistor is configuredto receive the reference voltage; a third transistor coupled in serieswith a fourth transistor, wherein the first signal is provided at a nodebetween the third transistor and the fourth transistor; and a fifthtransistor coupled in series with a sixth transistor, wherein the secondsignal is provided at a node between the fifth transistor and the sixthtransistor.